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SL6440
HIGH LEVEL MIXER
The SL6440 is a double balanced mixer intended for use in radio systems up to 150MHz. A special feature of the circuit allows external selection of the DC operating conditions by means of a resistor connected between pin 11 (bias) and Vcc When biased for a supply current of 50mA the SL6440 offers a 3rd order intermodulation intercept point of typically +30dBm, a value previously unobtainable with integrated circuits. This makes the device suitable for many applications where diode ring mixers had previously been used and offers the advantages of a voltage gain, low local oscillator drive requirement and superior isolation.
DG16 DP16
Fig.1 Pin connections - top view
FEATURES
s s s s +30dBm Input Intercept Point +15dBm Compression Point (1dB) Programmable Performance Full Military Temperature Range (SL644A)
ABSOLUTE MAXIMUM RATINGS
Supply voltage and output pins Maximum power dissipation (Derate above 25C: 8mW/C) Storage temperature range Programming current into pin 11 15V 1200mW -65C to +150C 50mA
APPLICATIONS
s s s Mixers in Radio Transceivers Phase Comparators Modulators
THERMAL CHARACTERISTICS
Thermal resistance: 0JA 0JC Time constant: Junction-Ambient Maximum chip temperature 125C/W 1.9 mins 150C
ORDERING INFORMATION
SL6440 A DG SL6440 C DP
ELECTRICAL CHARACTERISTICS
Test condltions (unless otherwise stated): VCC1 = 12V; VCC2 = 10V; IP = 25mA; Tamb = -55C to +125C (SL64440A), -30C to +85C (SL6440C) Local oscillator input level = 0dBm; Test circuit Fig.2. Characteristic Signal frequency 3dB point Oscillator frequency 3dB point 3rd order input intercept point Third order intermodulation distortion Second order intermodulation distortion 1dB compression point Noise figure Conversion gain Carrier leak to signal input Level of carrier at IF output Supply current Supply current (total from VCC1 & VCC2) Local oscillator input Local oscillator input impedance Signal input impedance Value Min. 100 100 Typ. 150 150 +30 -60 -75 15 11 -1 Max. Units MHz MHz dBm dB dB dBm Conditions
dB dB -40 dB -25 dBm 7 mA 60 mA 100 250 500 mV rms IP = 35mA 1.5 k 500 Single ended 1000 Differential NOTE Supply current in Pin 3 is equal to that in Pin 14 and is equal to IP See over. Vpin11 3Vbe 2.1V.
Two 0dBm input Signals VCC1 = 15V VCC2 = 12V VCC1 = 12V VCC2 = 10V Fig.8 test circuit 50 load Fig.2 Test circuit Fig.8 See applications information IP = 0
SL6440
CIRCUIT DESCRIPTION
The SL6440 is a high level mixer designed to have a linear RF performance. The linearity can be programmed using the IP pin (11). The output pins are open collector outputs so that the conversion gain and output loads can be chosen for the specific application. Since the outputs are open collectors they should be returned to a supply VCC1 through a load. The choice of VCC1 is important since it must be ensured that the voltage on pins 3 and 14 is not low enough to saturate the output transistors and so limit the signal swing unnecessarily. If the voltage on pins 3 and 14 is always greater than VCC2 the outputs will not saturate. The output frequency response will reduce as the output transistors near saturation. = (IP x RL) + VS + VCC2 Minimum VCC1 where IP = programmed current RL = DC load resistance = max signal swing at output VS if the signal swing is not known: minimum VCC1 = 2 (IP x RL) + VCC2 In this case the signal will be limiting at the input before the output saturates. The device has a separates supply (VCC2) for the oscillator buffer (pin 4).
VCC1
The current (IP) programmed into pin 11 can be supplied via a resistor from VCC1 or form a current source. The conversion gain is equal to RL IP for single-ended output 56.61 IP + 0.0785 2RL IP GdB = 20 Log for differential output 56.61 IP + 0.0785 Device dissipation is calculated using the formula mW diss = 2 IP VO + VPIP + VCC2 Diss where VO = voltage on pin 3 or pin 14 VP = voltage on pin 11 IP = programming current (mA) VCC2 Diss = dissipation obtained from graph (Fig.6) GdB = 20 Log As an example Fig.7 shows typical dissipations assuming VCC1 and VO are equal. This may not be the case in pratice and the device dissipation will have to be calculated for any particular application. Fig.5 shows the intermodulation performance against IP. The curves are independent of VCC1 and VCC2 but if VCC1 becomes too low the output signal swing cannot be accommodated, and if VCC2 becomes too low the circuit will not provide enough drive to sink the programmed current. Examples are shown of performance at various supply voltages. The current in pin 14 is equal to the current in pin 3 which is equal to the current in pin 11.
0.1 50 50 500
10
OUTPUT 3 14 11 0.1
-10
VCC2 10 0.1
4 0.001 13 RF INPUT
(dBm)
0
SL6440
5 0.001 50
LO INPUT
+10
50
6
12 0.001
10
(mA) TOTAL OUTPUT CURRENT (2IP)
20
30
Fig.2 Typical application and test circuit
Fig.3 Compression point v. total output current
0
10MHz WANTED OUTPUT
-1 -2 -3 -4 -5 -6 -7 -8 -9 -10 -11 -12 10 100
RF INPUT 0dBm LOCAL OSCILLATOR INPUT LEVEL VCC1 = 6V + VCC2 = 5V IP = 24mA VCC1 = 12V + + VCC2 = 10V
SIGNAL 10MHz HIGHER THAN LOCAL OSCILLATOR
+
+
1000
LOCAL OSCILLATOR FREQUENCY MHz
Fig.4 Frequency response at constant output IF
+ +
+
-1dBm COMPRESSION POINT
VCC1 = 15V VCC2 = 12V
VCC1 = 12V VCC2 = 10V LOCAL OSCILLATOR = 30MHz 0dBm RF INPUT = 40MHz IF = 10MHz
+ + +
40 50 60 70
SL6440
Fig.5 Intermodulation v. programming current
Fig.6 Supply current v. VCC2 (IP = 0)
APPLICATIONS
The SL6440 can be used with differential or singleended inputs and outputs. A balanced input will give bettercarrier leak The high input impedanceallowsstepup transformers to be used if desired, whilst high output impedance allows a choice of output impedance and conversion gain. Fig. 2 shows the simplest application circuit. The input and output are single-ended and Ip is supplied from VCC1 via a resistor. Increasing RL will increase the conversion gain, care being taken to choose a suitable value for VCC1. Fig. 8 shows an application with balanced input, for improved carrier leak, and balanced output for increased conversion gain. A lower VCC1 giving lower device dissipation can be used with this arrangement.
DESIGN PROCEDURE
1. Decide on input configuration using local oscillator data. If using transformer on input, decide on ratio from noise considerations. 2. Decide on output configuration and value of conversion gain required. 3. Decide on value of lP and VCC2 using intermodulation and compression point graphs. 4. Using values of conversion gain, VCC2, load and Ip already chosen, decide on value of VCC1. 5. Calculate device dissipation and decide whether heatsink is required from maximum operating temperature conslderatlons.
Fig.7 Device dissipation v. IP
Fig.8 Typical application circuit for highest performance
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